# 19.4 Load-dependent properties of resonant converters - PowerPoint PPT Presentation

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19.4 Load-dependent properties of resonant converters. Resonant inverter design objectives: 1. Operate with a specified load characteristic and range of operating points With a nonlinear load, must properly match inverter output characteristic to load characteristic

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19.4 Load-dependent properties of resonant converters

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### 19.4 Load-dependent propertiesof resonant converters

• Resonant inverter design objectives:

• 1. Operate with a specified load characteristic and range of operating points

• With a nonlinear load, must properly match inverter output characteristic to load characteristic

• 2. Obtain zero-voltage switching or zero-current switching

• Preferably, obtain these properties at all loads

• Could allow ZVS property to be lost at light load, if necessary

• 3. Minimize transistor currents and conduction losses

• To obtain good efficiency at light load, the transistor current should scale proportionally to load current (in resonant converters, it often doesn’t!)

### Topics of DiscussionSection 19.4

• Inverter output i-v characteristics

• Two theorems

• Dependence of transistor current on load current

• Dependence of zero-voltage/zero-current switching on load resistance

• Simple, intuitive frequency-domain approach to design of resonant converter

• Examples and interpretation

• Series

• Parallel

• LCC

### Inverter output characteristics

• Let H be the open-circuit (R) transfer function:

and let Zo0 be the output impedance (with vishort-circuit). Then,

This result can be rearranged to obtain

The output voltage magnitude is:

Hence, at a given frequency, the output characteristic (i.e., the relation between ||vo|| and ||io||) of any resonant inverter of this class is elliptical.

with

### Inverter output characteristics

• General resonant inverter output characteristics are elliptical, of the form

This result is valid provided that (i)the resonant network is purely reactive, and (ii) the load is purely resistive.

### Matching ellipseto application requirements

Electronic ballast

Electrosurgical generator

### Input impedance of the resonant tank networkAppendix C: Section C.4.4

Expressing the tank input impedance as a function of the load resistance R:

where

### ZN and ZD

ZD is equal to the tank output impedance under the condition that the tank input source vs1 is open-circuited. ZD = Zo

ZN is equal to the tank output impedance under the condition that the tank input source vs1 is short-circuited. ZN = Zo0

### Magnitude of the tank input impedance

If the tank network is purely reactive, then each of its impedances and transfer functions have zero real parts, and the tank input and output impedances are imaginary quantities. Hence, we can express the input impedance magnitude as follows:

### A Theorem relating transistor current variations to load resistance R

• Theorem 1: If the tank network is purely reactive, then its input impedance || Zi || is a monotonic function of the load resistance R.

• So as the load resistance R varies from 0 to , the resonant network input impedance || Zi || varies monotonically from the short-circuit value|| Zi0 || to the open-circuit value || Zi ||.

• The impedances || Zi || and || Zi0 || are easy to construct.

• If you want to minimize the circulating tank currents at light load, maximize || Zi ||.

• Note: for many inverters, || Zi || < || Zi0 || ! The no-load transistor current is therefore greater than the short-circuit transistor current.

### Proof of Theorem 1

• Differentiate:

• Previously shown:

• Derivative has roots at:

So the resonant network input impedance is a monotonic function of R, over the range 0 < R < .

In the special case || Zi0 ||=|| Zi||,|| Zi || is independent of R.

### Example: || Zi|| of LCC

• for f < fm, || Zi|| increases with increasing R .

• for f > fm, || Zi|| decreases with increasing R .

• at a given frequency f, || Zi|| is a monotonic function of R.

• It’s not necessary to draw the entire plot: just construct || Zi0|| and || Zi||.

### Discussion: LCC

LCC example

• || Zi0|| and || Zi|| both represent series resonant impedances, whose Bode diagrams are easily constructed.

• || Zi0|| and || Zi|| intersect at frequency fm.

• For f < fm

then || Zi0|| < || Zi|| ; hence transistor current decreases as load current decreases

• For f > fm

then || Zi0|| > || Zi|| ; hence transistor current increases as load current decreases, and transistor current is greater than or equal to short-circuit current for all R

### Discussion —series and parallel

• No-load transistor current = 0, both above and below resonance.

• ZCS below resonance, ZVS above resonance

• Above resonance: no-load transistor current is greater than short-circuit transistor current. ZVS.

• Below resonance: no-load transistor current is less than short-circuit current (for f <fm), but determined by || Zi||. ZCS.

### A Theorem relating the ZVS/ZCS boundary to load resistance R

• Theorem 2: If the tank network is purely reactive, then the boundary between zero-current switching and zero-voltage switching occurs when the load resistance R is equal to the critical value Rcrit, given by

It is assumed that zero-current switching (ZCS) occurs when the tank input impedance is capacitive in nature, while zero-voltage switching (ZVS) occurs when the tank is inductive in nature. This assumption gives a necessary but not sufficient condition for ZVS when significant semiconductor output capacitance is present.

### Proof of Theorem 2

Note that Zi, Zo0, and Zo have zero real parts. Hence,

• Previously shown:

If ZCS occurs when Ziis capacitive, while ZVS occurs when Ziis inductive, then the boundary is determined by Zi= 0. Hence, the critical load Rcrit is the resistance which causes the imaginary part of Zito be zero:

Solution for Rcrit yields

### Discussion —Theorem 2

• Again, Zi, Zi0, and Zo0 are pure imaginary quantities.

• If Zi and Zi0 have the same phase (both inductive or both capacitive), then there is no real solution for Rcrit.

• Hence, if at a given frequency Zi and Zi0 are both capacitive, then ZCS occurs for all loads. If Zi and Zi0 are both inductive, then ZVS occurs for all loads.

• If Zi and Zi0 have opposite phase (one is capacitive and the other is inductive), then there is a real solution for Rcrit. The boundary between ZVS and ZCS operation is then given by R = Rcrit.

• Note that R = || Zo0|| corresponds to operation at matched load with maximum output power. The boundary is expressed in terms of this matched load impedance, and the ratio Zi / Zi0.

### LCC example

• f > f: ZVS occurs for all R

• f < f0: ZCS occurs for all R

• f0 < f < f, ZVS occurs forR< Rcrit, and ZCS occurs forR> Rcrit.

• Note that R = || Zo0|| corresponds to operation at matched load with maximum output power. The boundary is expressed in terms of this matched load impedance, and the ratio Zi / Zi0.

### LCC example, continued

Typical dependence of Rcrit and matched-load impedance || Zo0 || on frequency f, LCC example.

Typical dependence of tank input impedance phase vs. load R and frequency, LCC example.

### 19.4.4 Design Example

• Select resonant tank elements to design a resonant inverter that meets the following requirements:

• Switching frequency fs = 100 kHz

• Input voltage Vg = 160 V

• Inverter is capable of producing a peak open circuit output voltage of 400 V

• Inverter can produce a nominal output of 150 Vrms at 25 W

### Preliminary calculations

• The requirements imply that the inverter tank circuit have an open-circuit transfer function of:

The required short-circuit current can be found by solving the elliptical output characteristic for Isc:

hence

Use the requirements to evaluate the above:

• Matched load therefore occurs at the operating point

Hence the tank should be designed such that its output impedance is

### Solving for the tank elements

• Let’s design an LCC tank network for this example

The impedances of the series and shunt branches can be represented by the reactances

### Analysis in terms of Xs and Xp

• The transfer function is given by the voltage divider equation:

The output impedance is given by the parallel combination:

Solve for Xs and Xp:

### Evaluate tank element values

• The capacitance Cp should therefore be chosen as follows:

The reactance of the series branch should be

### DiscussionChoice of series branch elements

• The series branch is comprised of two elements L and Cs, but there is only one design parameter: Xs = 733 Ω. Hence, there is an additional degree of freedom, and one of the elements can be arbitrarily chosen.

• This occurs because the requirements are specified at only one operating frequency. Any choice of L and Cs, that satisfies Xs = 733 Ω will meet the requirements, but the behavior at switching frequencies other than 100 kHz will differ.

• Given a choice for Cs, L must be chosen according to:

For example, Cs = 3Cp = 3.2 nF leads to L = 1.96 µH

### Rcrit

• For the LCC tank network chosen, Rcrit is determined by the parameters of the output ellipse, i.e., by the specification of Vg, Voc, and Isc. Note that Zo is equal to jXp. One can find the following expression for Rcrit:

Since Zo0 and H  are determined uniquely by the operating point requirements, then Rcrit is also. Other, more complex tank circuits may have more degrees of freedom that allow Rcrit to be independently chosen.

Evaluation of the above equation leads to Rcrit = 1466 Ω. Hence ZVS for R < 1466 Ω, and the nominal operating point with R = 900 Ω has ZVS.

### Converter performance

• For this design, the salient tank frequencies are

• (note that fs is nearly equal to fm, so the transistor current should be nearly independent of load)

The open-circuit tank input impedance is

So when the load is open-circuited, the transistor current is